Method, transmitter, structure, transceiver and access point for provision of multi-carrier on-off keying signal

ABSTRACT

A method of transmitting an On-Off Keying, OOK, signal includes an ON waveform and an OFF waveform forming a pattern representing transmitted information. The method includes obtaining a basic baseband waveform; scrambling the basic baseband waveform by applying a first binary randomised sequence where one of the binary values cause transformation to a complex conjugate, modulating the information to be transmitted by applying the scrambled basic baseband waveform for the ON waveform and applying no waveform for the OFF waveform; and transmitting the modulated information.

CROSS REFERENCE TO RELATED APPLICATIONS

This Application is a continuation of U.S. patent application Ser. No.17/263,218, filed Jan. 26, 2021, entitled “METHOD, TRANSMITTER,STRUCTURE, TRANSCEIVER AND ACCESS POINT FOR PROVISION OF MULTI-CARRIERON-OFF KEYING SIGNAL”, which claims priority to InternationalApplication Serial No. PCT/EP2019/068123, filed Jul. 5, 2019, whichclaims the benefit of U.S. Provisional Application No. 62/712,407, filedJul. 31, 2018, the entirety of both of which is incorporated herein byreference.

TECHNICAL FIELD

The present disclosure generally relates to an approach for transmittingan On-Off Keying, OOK, signal. In particular, the disclosure relates tolow-complexity implementation of providing and transmitting such asignal.

BACKGROUND

On-off keying (OOK) is a binary modulation, where a logical one isrepresented with sending a signal (ON) whereas a logical zero isrepresented by not sending a signal (OFF). Here, one of the states mayrepresent one binary symbol value and the other state will thenrepresent the other binary symbol. Patterns of the states may representa binary symbol, e.g. as provided through Manchester coding.

Wake-up receivers (WUR), sometimes also referred to as wake-up radios,provide a means to significantly reduce the power consumption inreceivers used in wireless communication. The idea with a WUR is that itcan be based on a very relaxed architecture, as it only needs to be ableto detect the presence of a wake-up signal but will not be used for anydata reception.

A feasible modulation for the wake-up packet (WUP), i.e., the signalsent to the WUR, is the OOK. In the IEEE 802.11 draft specification, seeIEEE 802.11-18/0152r5 with title “Proposed Draft WUR PHY Specification”,the WUP is called WUR Physical Protocol Data Unit (PPDU).

There are currently activities ongoing in the IEEE 802.11 task group(TG) named IEEE 802.11ba to standardize the physical (PHY) and mediumaccess (MAC) layers for a Wake-Up Radio to be used as a companion radioto an IEEE 802.11 primary communications radio (PCR) with the merepurpose to significantly reduce the power consumption of stationsequipped with both WUR and PCR.

FIG. 1 illustrates the WUR and PCR, e.g. for IEEE 802.11 communication,share the same antenna. When the WUR is turned on and waiting for thewake-up message, the IEEE 802.11 chipset can be switched off to preserveenergy. Once the wake-up message is received by the WUR, it wakes up thePCR and starts e.g. Wi-Fi communication with an access point (AP).

In IEEE 802.11-18/0152r5 with title “Proposed Draft WUR PHYSpecification” mentioned above, it is proposed to apply Manchestercoding to the information bits of the WUP. That is, for example alogical “0” is encoded as “10” and a logical “1” as “01”. Therefore,every data symbol comprises an “ON” part (where there is energy) and an“OFF” part, where there is no energy. In addition, it is proposed togenerate the WUP by means of an inverse fast Fourier transform (IFFT),as this block is already available in Wi-Fi transmitters supporting e.g.IEEE 802.11a/g/n/ac. Specifically, an approach discussed for generatingthe OOK is to use the 13 sub-carriers in the centre, and then populatingthese with some signal to represent ON and to not transmit anything atall to represent OFF. This approach differs slightly from traditionalOOK in that multiple carriers are used to generate the ON part.Therefore, the OOK scheme being standardized in IEEE 802.11ba isreferred to as multicarrier OOK (MC-OOK). The IFFT has 64 points and isoperating at a sampling rate of 20 MHz, and just as for ordinaryorthogonal frequency division multiplexing (OFDM) a cyclic prefix (CP)is added after the IFFT operation in order to have the OFDM symbolduration as being used in IEEE 802.11a/g/n/ac. An important feature ofMC-OOK is that the same OFDM symbol is used to generate MC-OOK. In otherwords, the same frequency domain symbols are used to populate thenon-zero subcarriers for all data symbols. Using the same OFDM symbol togenerate the “ON” part of every Manchester coded data symbol has someadvantages. For example, it allows coherent reception of the MC-OOK.Moreover, the generation of ON waveform can be inclined to have low peakto average power ratio and/or can be inclined for performance.

FIG. 2 schematically illustrates a traditional structure for OOKgeneration. The signal to be transmitted, e.g. the bits for the WUP, isfor example Manchester coded in a Manchester-based encoder 200. Theencoded signal controls which output signal to provide during a nextsymbol time, T_(sym), e.g. by a switch arrangement 202. T_(sym) may forexample be 2 μs for a high data rate or it may be 4 μs for a low datarate. The switching is made between a signal provided by an ON signalwaveform generator (WG) 204, which in the present approach provides amulticarrier signal mimicking the desired ON signal, and a signalprovided by an OFF signal waveform generator (WG) 206, which in thepresent approach provides a zero signal. The switching arrangement 202outputs a signal sequence to be transmitted, which is traditionallyprocessed and wirelessly transmitted.

The multicarrier signal referred to above is normally generated by meansof an inverse fast Fourier transform (IFFT), as this block may alreadybe available in some transmitters such as for example Wi-Fi transmitterssupporting e.g. IEEE 802.11a/g/n/ac. FIG. 3 schematically illustrates astructure for generating a basic baseband waveform (BW) using IFFT. Anexample approach for generating the multicarrier signal to represent aWUP is to use 13 sub-carriers in the centre of an OFDM multi-carriersignal, and populating these 13 sub-carriers with a signal to representON and to not transmit anything at all to represent OFF. This may bereferred to as multicarrier OOK (MC-OOK). In one example, the IFFT has64 points and is operating at a sampling rate of 20 MHz, and just as forordinary orthogonal frequency division multiplexing (OFDM) a cyclicprefix (CP) is added after the IFFT operation in order to have the OFDMsymbol duration as being used in IEEE 802.11a/g/n/ac. In some examplesof MC-OOK for a WUP, the same OFDM symbol is used. In other words, thesame frequency domain symbols are used to populate the non-zerosubcarriers for all data symbols. Using the same OFDM symbol to generatethe “ON” part of every Manchester coded data symbol may result in strongperiodic time correlations in the data part of the WUP. Thesecorrelations give rise to spectral lines, as illustrated in FIG. 4,which are spikes in the Power Spectral Density (PSD) of the WUP. Thesespectral lines may in some examples be undesirable because there may belocal geographic regulations that limit the power that can betransmitted in narrow portions of the spectrum.

The present disclosure aims for providing improvements on generation ofthe ON part.

MC-OOK is used to generate the WUP. Moreover, the same OFDM symbol isused to generate the “ON” part of every Manchester coded informationsymbol. Because the OFDM symbol is repeated in every information symbol,there are strong periodic time correlations in the payload of the WUP.These correlations give rise to spectral lines, which are spikes in thePower Spectral Density (PSD) of the WUP. The PSD of the generatedmulticarrier signal is illustrated in FIG. 4.

For example, in the USA, the Federal Communications Commission requiresthat digitally modulated signals in the 2.4 MHz band transmit a powerless than 8 dBm in any 3 kHz band. Hence, the presence of spectral linesmay limit the maximum transmit power for the WUP to a value that is lessthan what would be allowed if spectral lines were not present.

FIG. 5 schematically illustrates a structure for a phase randomisationtechnique to smooth power spectral density spikes of a signal as of FIG.4. The approach is that each symbol is binary rotated with either 0 or180 degrees (i.e., multiplied with either +1 or −1, such that a mutualphase difference of π is achieved). The rotation is chosenpseudo-randomly. This symbol randomization method is illustrated in FIG.5. A pseudo-random bit stream is used to generate binary phase shiftkeyed, BPSK, symbols, taking on the values +1 and −1, and the Onwaveform is then multiplied by this binary symbol.

FIG. 6 gives an illustration of how the symbol randomization techniqueproposed in above eliminates the spectral lines. Diagrams of FIG. 4 andFIG. 6 have been produced using the same basic baseband waveformgenerated by the waveform generator. The difference is that the basicbaseband waveform has been used to produce the diagram of FIG. 4, whilethe scrambled waveform has been used to produce the diagram of FIG. 6.

Although the spectral lines are removed, the PSD is dependent on thefrequency response of the On waveform, since phase randomizationdiscussed above does not alter the energy distribution over frequency.The PSD shown in FIG. 6 exhibits lack of symmetry and flatness. Lack ofspectral flatness is a disadvantage in some regulatory domains. Forexample, in Europe, for equipment operating in the 2.4 GHz band andusing wideband modulation techniques, the maximum power spectral densityis limited to 10 mW per MHz. Hence, subject to this PSD constraint, theoutput power is maximized when the PSD is flat. For example, due to thePSD limits in Europe, a WUP having a PSD as in FIG. 6 would have a totaloutput power of 28 mW, whereas a signal having the same bandwidth (4MHz) but with a flat PSD could have a total output power of 40 mW (10mW/MHz×4 MHz). Therefore, an approach which yield improved spectralflatness is sought.

The above information disclosed in this Background section is only forenhancement of understanding of the background of the disclosure andtherefore it may contain information that does not form the prior artthat is already known to a person of ordinary skill in the art.

SUMMARY

The disclosure is based on the inventor's realization that randomlyapplying complex conjugation cause flattening of the PSD.

According to a first aspect, there is provided a method of transmittingan On-Off Keying, OOK, signal which comprises an ON waveform and an OFFwaveform forming a pattern representing transmitted information. Themethod comprises obtaining a basic baseband waveform, scrambling thebasic baseband waveform by applying a first binary randomised sequencewhere one of the binary values cause transformation to a complexconjugate, modulating the information to be transmitted by applying thescrambled basic baseband waveform for the ON waveform and applying nowaveform for the OFF waveform, and transmitting the modulatedinformation.

The obtaining of the basic baseband waveform may comprise generating anOrthogonal Frequency Division Multiplexing signal mimicking a desiredbaseband waveform. The desired baseband waveform may correspond to amulticarrier on-off keying, MC-OOK, symbol.

The scrambling of the basic baseband waveform may comprise applying asecond binary randomised sequence where binary values apply phaserotations which are mutually separated by π. The first randomisedsequence may be generated in a shift register mechanism representing afirst polynomial and the second randomised sequence is generated in ashift register mechanism representing a second polynomial different fromthe first polynomial. The shift register mechanism may use a singleshift register for the generation of both the first and the secondbinary randomised sequences, where the first binary randomised sequenceis tapped at a first position of the single shift register and thesecond binary randomised sequence is tapped at a second position of thesingle shift register, and the first and second positions of the singleshift register are different.

According to a second aspect, there is provided a transmitter fortransmitting an On-Off Keying, OOK, signal which comprises an ONwaveform and an OFF waveform forming a pattern representing transmittedinformation. The transmitter comprises a basic waveform input arrangedto obtain a basic baseband waveform, a scrambler arranged to scramblethe basic baseband waveform by applying a first binary randomisedsequence where one of the binary values cause transformation to acomplex conjugate, a modulator arranged to modulate the information tobe transmitted by applying the scrambled basic baseband waveform for theON waveform and applying no waveform for the OFF waveform, and atransmitter circuit arranged to transmit the modulated information.

The transmitter may comprise a basic baseband waveform generator,wherein the basic baseband waveform generator is arranged to generatethe basic baseband waveform as an Orthogonal Frequency DivisionMultiplex signal mimicking a desired baseband waveform, and is arrangedto provide the basic baseband waveform to the basic waveform input. Thedesired baseband waveform may correspond to a multicarrier on-offkeying, MC-OOK, symbol.

The scrambler may be arranged to apply a second binary randomisedsequence where binary values apply phase rotations which are mutuallyseparated by π. The first randomised sequence may be generated in ashift register mechanism representing a first polynomial and the secondrandomised sequence is generated in a shift register mechanismrepresenting a second polynomial different from the first polynomial.The transmitter may comprise a shift register, wherein the shiftregister mechanism uses the shift register for the generation of boththe first and the second binary randomised sequences, where the firstbinary randomised sequence is tapped at a first position of the shiftregister and the second binary randomised sequence is tapped at a secondposition of the shift register, and the first and second positions ofthe shift register are different.

According to a third aspect, there is provided a computer programcomprising instructions which, when executed on a processor of acommunication apparatus, causes the communication apparatus to performthe method according to the first aspect.

According to a fourth aspect, there is provided a structure forgenerating sequences. The structure comprises a binary shift register, afeedback structure connected to the shift register arranged to define alinear feedback shift register according to a polynomial, a first outputarranged to collect one or more state values from a first group ofelements of the shift register, wherein said one or more state valuesfrom the first group form a value of a first sequence, and a secondoutput arranged to collect one or more state values from a second groupof elements of the shift register, wherein said one or more state valuesfrom the second group form a value of a second sequence, and wherein noelement of the second group belongs to the first group.

The second output may be arranged to collect state values from thesecond group of element, the second group comprising a plurality ofelements of the shift register such that the second sequence comprisessymbols having more than two possible values. Alternatively, the secondsequence is a binary sequence. The second output may then be arranged tocollect state values from the second group of elements, where the secondgroup comprises a single element of the shift register.

The first output may be arranged to collect state values from the firstgroup comprising a plurality of elements of the shift register such thatthe first sequence comprises symbols having more than two possiblevalues. Alternatively, the first sequence is a binary sequence. Thefirst output may then be arranged to collect state values from the firstgroup of elements, where the first group comprises a single element ofthe shift register.

According to a fifth aspect, there is provided a transceiver comprisinga transmitter according to the second aspect, and a structure accordingto the fourth aspect, wherein the structure is arranged to provide thefirst and second sequences for the transmitter.

According to a sixth aspect, there is provided an access point of awireless network, wherein the access point is arranged to transmit awake-up packet using multicarrier on-off keying. The access pointcomprises a transmitter according to the second aspect or a transceiveraccording to the fifth aspect.

The approach according to some embodiments flattens PSD of the signalused for the WUP, and for some embodiments eliminates spectral lines. Anadvantage is possibility for increased output power in regulatorydomains that impose limits on the PSD.

An advantage of some embodiments is the possibility for very lowimplementation complexity.

An advantage of some embodiments is that the approach preserves theproperties of the On waveform. For example, if the On waveform has beendesigned to have low peak-to-average power ratio, PAPR, then the methodof the disclosure preserves the PAPR. Similarly, if the On waveform hasbeen optimized for performance in some propagation channel, then thedisclosed approach preserves the performance.

An advantage of some embodiments is the low complexity of implementationof a structure which provides multiple sequences with low mutualcorrelation.

BRIEF DESCRIPTION OF THE DRAWINGS

The above, as well as additional objects, features and advantages of thepresent disclosure, will be better understood through the followingillustrative and non-limiting detailed description of preferredembodiments of the present disclosure, with reference to the appendeddrawings.

FIG. 1 schematically illustrates a receiver having a traditional WUR andPCR structure.

FIG. 2 schematically illustrates a traditional OOK structure.

FIG. 3 schematically illustrates a structure for generating a basicbaseband waveform using IFFT.

FIG. 4 is a signal diagram illustrating power spectral density of abasic baseband waveform generated by a structure according to FIG. 3.

FIG. 5 schematically illustrates a structure for a phase randomisationtechnique to smooth power spectral density spikes of a signal as of FIG.4.

FIG. 6 is a signal diagram illustrating power spectral density of asmoothened waveform by the structure of FIG. 5.

FIG. 7 schematically illustrate a structure for flattening powerspectral density of a waveform according to an embodiment.

FIG. 8 illustrates signal diagrams of power spectral densities of asignal (Cf. FIG. 6) and a complex conjugate of the signal.

FIG. 9 illustrates an alternative structure for flattening powerspectral density of a waveform according to an embodiment.

FIG. 10 is a signal diagram illustrating a flattened power spectraldensity using an embodiment.

FIG. 11 schematically illustrates a transmitter according to anembodiment.

FIG. 12 schematically illustrates a transmitter according to anembodiment.

FIG. 13 schematically illustrates a transmitter according to anembodiment.

FIG. 14 schematically illustrates a linear feedback shift register forgenerating a first sequence and an addon tap to extract a secondsequence according to an embodiment.

FIG. 15 schematically illustrates a linear feedback shift register forgenerating a first sequence and an addon tap mechanism to extract asecond sequence according to an example.

FIG. 16 schematically illustrates a linear feedback shift register forgenerating a first sequence and an addon tap mechanism to extract asecond sequence according to an embodiment.

FIG. 17 schematically illustrates a transmitter according to anembodiment.

FIG. 18 is a signal diagram illustrating power spectral density of abasic baseband waveform generated when applying a structure as of FIG.15.

FIG. 19 is a flow chart illustrating a method according to anembodiment.

FIG. 20 is a block diagram schematically illustrating a network nodeaccording to an embodiment.

FIG. 21 schematically illustrates a computer-readable medium and aprocessing device.

DETAILED DESCRIPTION

FIG. 7 schematically illustrate a structure for flattening powerspectral density of a waveform according to an embodiment. A binary bitsequence with proper randomisation is provided, and for each bit valueb1 a baseband waveform is substituted by its complex conjugate for oneof the states of the bit value and kept unchanged for the other state ofthe bit value. The randomised complex conjugation will flatten the PSDof the output of the structure.

FIG. 8 illustrates signal diagrams of power spectral densities of asignal (Cf. FIG. 6) and a complex conjugate of the signal. By therandomised substitution with the complex conjugate version of the basicbaseband waveform, an alternative OFDM signal is randomly provided, withspectral content as illustrated to the right in FIG. 8. The alternativeOFDM signal provides the same envelope as the basic baseband waveform,but with a different spectral content. This is due to that the waveformobtained by complex conjugating a time domain OFDM waveform can also begenerated by transforming to the time domain a frequency domain signalcomprising frequency domain symbols that are the complex conjugates ofthe frequency domain symbols of the original signal, and reversing theorder of the subcarriers. For example, if an OFDM signal is generatedfrom complex-valued frequency domain symbols X_(k), where k=−M, . . . ,M, by means of an IFFT, then the complex conjugate of said OFDM signalcan be generated by applying an inverse discrete Fourier transform tothe frequency domain symbols X*_(−k), where the star * representscomplex conjugation and the minus sign in the index k indicates reversalof the order of the subcarriers. The randomised provision of thevariants, i.e. sometimes with spectral content as illustrated to theleft in FIG. 8 and sometimes with spectral content as illustrated to theright in FIG. 8, provides for the flatter waveform in average, whichwill be demonstrated with reference to FIG. 10 below illustrating asimulated result of one embodiment of the approach.

FIG. 9 illustrates an alternative structure for flattening powerspectral density of a waveform according to an embodiment. Here, thespectral line suppression feature demonstrated with FIG. 5 is appliedtogether with an approach similar to the one demonstrated with referenceto FIG. 7. This structure will thus do spectral line suppression and PSDflattening.

FIG. 10 is a signal diagram illustrating a flattened power spectraldensity using an embodiment. This is for example a result achieved whenapplying the structure demonstrated with reference to FIG. 9 on a basicbaseband signal generated by a generator structure as demonstrated withreference to FIG. 3. The PSD is fairly flat and free from spectrallines, and thus provides good performance for use in an OOK provisionstructure.

Referring back to the discussion in the background section about thelimitations in output power, a discussion about the benefits of theflattened PSD illustrated by the diagram of FIG. 10 will now be given.Subject to the PSD limits in for example Europe, a WUP having a PSD asin the diagram of FIG. 10 would have a total output power of 35 mW,given the same other features as of the example in the backgroundsection. Note that although the same basic baseband On waveform is usedto generate FIG. 6 and FIG. 10, the output power in PSD limitedregulatory domains is 1 dB larger if the transmitter is implementedaccording to the approach providing the PSD as of FIG. 10 than accordingto traditional techniques providing the PSD as of FIG. 6.

FIG. 11 schematically illustrates a transmitter according to anembodiment. In brief, the transmitter is arranged for OOK similar to thestructure which has been demonstrated with reference to FIG. 2 but witha PSD flattening structure similar to the structure which has beendemonstrated with reference to FIG. 7. The ON waveform generator (WG)providing the waveform to the PSD flattening structure may be similar tothe generator demonstrated with reference to FIG. 3.

FIG. 12 schematically illustrates a transmitter according to anembodiment. In brief, the transmitter is arranged for OOK similar to thestructure which has been demonstrated with reference to FIG. 2 but witha PSD flattening structure similar to the structure which has beendemonstrated with reference to FIG. 7 and a spectral line suppressionstructure similar to the one which has been demonstrated with referenceto FIG. 5. The ON waveform generator (WG) providing the waveform to thePSD flattening structure may be similar to the generator demonstratedwith reference to FIG. 3.

FIG. 13 schematically illustrates a transmitter according to anembodiment. In brief, the transmitter has a similar structure as the onedemonstrated with reference to FIG. 12, but with the spectral linesuppression structure similar to the one which has been demonstratedwith reference to FIG. 5 connected to the waveform generator and thenthe PSD flattening structure similar to the structure which has beendemonstrated with reference to FIG. 7 provided between the spectral linesuppression structure and the OOK structure.

The bit sequences provided to the PSD flattening structure for providinga randomised application of the complex conjugate may be provided in avariety of ways. One way is to use a pseudorandom sequence generatorbased on a linear feedback shift register. Another way is to collect asequence from a look-up table. Below, with reference to FIGS. 14 to 16,there are demonstrated approaches for achieving multiple sequences froma single shift register structure. The multiple sequences may be desiredfor example for the structures demonstrated with reference to FIGS. 12and 13 where the PSD flattening structure demands one sequence and thespectral line suppression structure demands one sequence. For the sakeof not risk causing new kinds of spurs in the signal for the OOKstructure, it is desired to have separate sequences in those cases,which sequences have limited mutual correlations. The approachesdemonstrated with reference to FIGS. 14 to 16 have the advantage ofkeeping implementation complexity low.

An alternative way of flattening a signal as discussed above is taughtin international application PCT/EP2018/066984, which is hereincorporated by reference in its entirety. That approach comprisestransmitting a first on-off keyed signal corresponding to the datasymbols, the first signal comprising a plurality of on periods and aplurality of off periods. Each on period comprises a first signalportion cyclically shifted within the on period by a respective randomor pseudorandom factor. The cyclic shifting of the first signal portionmay be performed within the on period. For example, the first signalportion may be shifted in the on period by a factor such as a delay orpercentage, and any part of the first signal that is shifted outside ofthe on period may be reintroduced into the on period at the opposite endof the on period. In this way, for example, the on period may in someexamples remain filled with a signal formed from the first signalportion. In some examples, therefore, the first signal may have aflatter frequency response than other signals. In an example, Manchestercoding may be applied to the data part of a wake up packet (WUP). Forexample, a logical “0” is encoded as “10” and a logical “1” as “01”.Therefore, every data symbol comprises an “ON” part (where there isenergy) and an “OFF” part, where there is no energy, wherein the orderof these parts is dependent on the data symbol. In addition, the WUP maybe generated in some examples by means of an inverse fast Fouriertransform (IFFT), as this block may already be available in sometransmitters such as for example Wi-Fi transmitters supporting e.g. IEEE802.11a/g/n/ac. An example approach for generating the OOK signalrepresenting a WUP is to use the 13 sub-carriers in the centre of anOFDM multi-carrier signal, and populating these 13 sub-carriers with asignal to represent ON and to not transmit anything at all to representOFF, similar as demonstrated with reference to FIG. 3. This may bereferred to as multicarrier OOK (MC-OOK). In one example, the IFFT has64 points and is operating at a sampling rate of 20 MHz, and just as forordinary orthogonal frequency division multiplexing (OFDM) a cyclicprefix (CP) is added after the IFFT operation in order to have the OFDMsymbol duration as being used in 802.11a/g/n/ac. In some examples ofMC-OOK for a WUP, the same OFDM symbol is used. In other words, the samefrequency domain symbols are used to populate the non-zero subcarriersfor all data symbols. Using the same OFDM symbol to generate the “ON”part of every Manchester coded data symbol may result in strong periodictime correlations in the data part of the WUP. These correlations giverise to spectral lines, which are spikes in the Power Spectral Density(PSD) of the WUP. These spectral lines may in some examples beundesirable because there may be local geographic regulations that limitthe power that can be transmitted in narrow portions of the spectrum.

In a first example embodiment, a signal is transmitted from a singleantenna. Suppose that the data part of the WUP consists of a number N ofOFDM symbols. This example embodiment consists of the following steps:

1. Determine a set of K delays, K≥2. These are {T₁ ^(CS), . . . , T_(K)^(CS)}.

2. Generate a random or pseudorandom sequence consisting of N integerstaking values between 1 and K. These are {m₁, . . . , m_(N)}.

3. Apply a random or pseudorandom cyclic shift to each of the OFDMsymbols corresponding to the “ON” parts of the data symbols, wherein thecyclic shift corresponds to one of the N integers in the sequence. Forexample, apply the delay T_(m) _(n) ^(CS) (a negative value) to the OFDMsymbol corresponding to the “ON” part of the n-th data symbol. That is,if s(t), 0≤t<T_(S) is the time domain signal corresponding to the “ON”part, having a duration T_(S), then the cyclic shift s_(CS) (t; T_(m)_(n) ^(CS)) of s(t) by the delay T_(m) _(n) ^(CS)≤0 is generated bysetting:

${s_{CS}( {t;T_{m_{n}}^{CS}} )} = \{ \begin{matrix}{s( {t - T_{m_{n}}^{CS}} )} & {if} & {0 \leq t < {T_{s} + T_{m_{n}}^{CS}}} \\{s( {t - T_{m_{n}}^{CS} - T_{s}} )} & {if} & {{T_{m_{n}}^{CS} + T_{s}} \leq t < T_{s}}\end{matrix} $

4. Transmit the MC-OOK signal, comprising the cyclically shifted OFDMsymbol s_(CS) (t; T_(m) _(n) ^(CS)) in the “ON” part of the n-th datasymbol.

In one particular example, T_(S)=4 μs. A set of K=8 cyclic shifts {T₁^(CS), . . . , T₈ ^(CS)} is defined as shown in the table below.

T₁ ^(CS) −0 ns T₂ ^(CS) −400 ns T₃ ^(CS) −800 ns T₄ ^(CS) −1200 ns T₅^(CS) −1600 ns T₆ ^(CS) −2000 ns T₇ ^(CS) −2400 ns T₈ ^(CS) −2800 ns

In another particular example, T_(S)=2 μs. A set of K=8 cyclic shifts{T₁ ^(CS), . . . , T₈ ^(CS)} is defined as shown in the table below.

T₁ ^(CS) −0 ns T₂ ^(CS) −400 ns T₃ ^(CS) −600 ns T₄ ^(CS) −800 ns T₅^(CS) −1000 ns T₆ ^(CS) −1200 ns T₇ ^(CS) −1400 ns T₈ ^(CS) −1800 ns

A sequence of random or pseudorandom integers having values between 1and 8 is generated for each data symbol, and a cyclic shift by thecorresponding delay is applied to the “ON” part of the signal for eachdata symbol. For example, if T_(S)=2 μs and the integer m generated forthe n-th data symbol is 6, then a cyclic shift of T₆ ^(CS)=1200 ns isapplied to the “ON” part of the n-th transmitted data symbol.

A suitable approach for generating pseudorandom sequence generation isdesired for this solution as well for the approach demonstrated withreference to FIGS. 1 to 13. As an example, consider the case where K isa power of 2, i.e. K=2^(p). The 802.11 standard utilizes the linearfeedback shift register with generator polynomial z⁻⁷+z⁻⁴+1 to generatepseudorandom bit sequences. Any of these sequences can be used, bygrouping the output in groups of p bits. Any such group can be mapped toan integer between 1 and K.

Another example embodiment involves transmission from multiple antennas(e.g. transmit diversity or spatial diversity). For each of theantennas, an MC-OOK signal is generated from data symbols according toany given multi-antenna transmit (TX) diversity technique. Then, theembodiment given for a single transmit antenna can be applied to asignal to be transmitted from each antenna. The TX diversity techniqueapplied to the signals from the antennas may comprise delay diversity(e.g. as used in the GSM cellular system) or cyclic delay diversity(e.g. as used in the LTE cellular system).

In an example, suppose that there are L transmit antennas, MC-OOK isused, and CSD is the TX diversity technique employed by the transmitter.In this case, cyclic delays Δ_(l), l=1, . . . , L are applied to theOFDM symbol s(t). Thus, the signal transmitted through the 1-th antennais s^(l)(t)=s_(CS)(t;Δ_(l)), where s_(CS)(t; Δ_(l)) denotes the cyclicshift of s(t) by Δ_(l) and is defined as given above for thesingle-antenna example. This example embodiment consists of thefollowing steps:

1. Determine a set of K delays, K≥2. These are {T₁ ^(CS), . . . , T_(K)^(CS)}.

2. Generate a random or pseudorandom sequence consisting of N integerstaking values between 1 and K. These are {m₁, . . . , m_(N)}.

3. For each of the L antennas, apply the delay T_(m) _(n) ^(CS) (anegative value) to the OFDM symbol corresponding to the “ON” part of then-th data symbol. That is, if s^(l)(t), 0≤t<T_(S) is the time domainsignal corresponding to the “ON” part, then for the l-th antenna, thecyclic shift s_(CS) ^(l) (t; T_(m) _(n) ^(CS)) of s^(l)(t) is generatedby applying a cyclic delay by T_(m) _(n) ^(CS). Note the delay T_(m)_(n) ^(CS) may change from one data symbol to the next.

4. Transmit the MC-OOK signal, comprising the cyclically shifted OFDMsymbol s_(CS) ^(l) (t; T_(m) _(n) ^(CS)) in the “ON” part of the n-thdata symbol in the signal transmitted through the l-th antenna.

As an example, if CSD is used, then:

${s_{CS}^{l}( {t;T_{m_{n}}^{CS}} )} = {{s( {t;{\Delta_{l} + T_{m_{n}}^{CS}}} )} = \{ \begin{matrix}{s( {t - \Delta_{l} - T_{m_{n}}^{CS}} )} & {if} & {0 \leq t < {\Delta_{l} + T_{s} + T_{m_{n}}^{CS}}} \\{s( {t - \Delta_{l} - T_{m_{n}}^{CS} - T_{s}} )} & {if} & {{\Delta_{l} + T_{m_{n}}^{CS} + T_{s}} \leq t < T_{s}}\end{matrix} }$

Cyclic shift symbol randomization suppresses spectral lines and flattensthe spectrum. In an example where T_(sym)=4 μs and there are 8 possiblesyclic shifts, by 0 ns, 400 ns, 800 ns, 1200 ns, 1600 ns, 2000 ns, 2400ns and 2800 ns.

A slight drawback of the cyclic shift symbol randomization technique isthat it can't eliminate spectral lines arising from the DC component inthe On waveform. A cyclic shift applied to an OFDM signal can beimplemented by a rotation of the frequency domain symbols. Thus, whenapplied to OFDM waveforms, cyclic shift randomization can be thought ofas randomization of the phases of the subcarriers. However, the rotationapplied to the DC subcarrier by any cyclic shift is zero, and hence thephase of the DC subcarrier can't be randomized by means of cyclic shiftrandomization. A practical solution to this drawback may be to usewaveforms without a DC component as On waveforms. This can be achievedby nulling or blanking the DC subcarrier of an OFDM waveform. However,there might be circumstances where having a non-null DC subcarrier isdesirable, for example to have more degrees of freedom to optimize theOn waveform for performance or for other metric.

Symbol randomization techniques that suppress spectral lines asdemonstrated with reference to FIG. 5 combined with cyclic shiftrandomization as demonstrated above provides for a low complexitytechnique to suppress spectral lines and flatten the spectrum. Astructure for achieving this is illustrated in FIG. 17, where an exampleof a low-complexity sequence generation as will be demonstrated below isapplied.

A well-known approach for generating pseudorandom sequences are theabove-mentioned linear feedback shift register using a properpolynomial. Considering the approaches demonstrated herein for removalof spectral lines and flattening of spectral properties of a signal,there is a desire for an efficient and low-resource consuming solutionfor producing two or more sequences. Here, the two or more sequences arepreferably having limited correlation not to risk introducing newundesired spurs in the signal. A straightforward solution is to have onegeneration mechanism for each sequence to generate, and to carefullyselect e.g. structure and polynomials of the respective generationmechanism to provide limited correlation. However, in this disclosure itis suggested an approach for generating two or more sequences from asingle shift register structure where register elements and their statesare reused for the different sequences. A basic sequence generated bythe structure will have the same properties as of a linear feedbackshift register. The additional generated sequences will not have thesame characteristics but will have low enough correlation for thepurposes of the signal shaping approaches of this disclosure and willalso have sufficient performance for other applications where multiplesequences with low correlation is desired.

An approach according to this disclosure is implemented in atransmitting network node, such as an access point, AP. An embodiment isillustrated in FIG. 17. The LFSR is updated every T_(sym).

FIG. 14 schematically illustrates a linear feedback shift register forgenerating a first sequence and an addon tap to extract a secondsequence according to an embodiment. The LFSR in this figure hasgenerator polynomial x⁻⁷+x⁻⁴+1, but other generator polynomials can beused. Referring back to the Figs illustrating OOK, The LFSR is updatedevery symbol time, T_(sym), and the bits b0 and b1 are read fromdifferent states of the LFSR. For example b0 may be extracted from thefirst position in the register, labelled X¹ in FIG. 14, while b1 may beextracted from the seventh position in the register, labelled X⁷ in FIG.14.

FIG. 15 schematically illustrates a structure comprising a LinearFeedback Shift Register (LFSR) with generator polynomial x⁻⁷+x⁻⁴+1 wherethe structure is used to generate a pseudo-random bit sequence, butother polynomials could be used. The register contains seven elementslabelled X¹ to X⁷. The bits b5 to b7 are extracted from the elements 5to 7 of the register. Moreover, the LFSR is updated every T_(sym). Notethat both phase randomization and cyclic shift randomization require asource of randomness, in order to generate random phase shifts andrandom cyclic shifts. Ideally, independent sources of randomness shouldbe used. However, for ease of implementation the same LFSR is used togenerate both the sequences.

A problem with the combined solution is that there is a strongcorrelation between the source of randomness used for the phaserandomizer (i.e. b7) and the source of randomness for the cyclic shiftrandomizer (i.e. b5, b6, b7). In a combined flattening and spectral linesuppression structure including e.g. a complex conjugation structure anda phase shifter, or a cyclic shifter and a phase shifter, this may causeremaining spectral lines as illustrated in the diagram of FIG. 18. Thereason is that in this example cyclic shift randomization imparts arandom phase shift by zero or 180 degrees to two of the subcarriers, butdue to the perfect correlation, the phase randomizer reverses the 180degrees phase shift, so that as a result these two subcarriers don'thave their phase randomized, resulting in the two spectral lines shownin FIG. 18. In order to eliminate spectral lines, the phases applied toeach subcarrier in the On waveform preferably have zero mean. Butbecause of the strong correlations, they may fail to do so. As anillustration, suppose that there are 8 possible cyclic shifts, by 0 ns,400 ns, 800 ns, 1200 ns, 1600 ns, 2000 ns, 2400 ns and 2800 ns.

Hence, since a symbol randomization technique based on a combination ofphase randomization and cyclic shift randomization is desirable, andsince due to ease of implementation it is also desirable to use only oneLFSR as source of randomness for both randomization techniques, it issought a method to achieve symbol randomization by means of acombination of phase randomization, cyclic shift randomization and usingonly one LFSR. The basic idea in the present disclosure is to create twosources of entropy or randomness from the same LFSR in such a way thatthe two randomization techniques are sufficiently decorrelated.

FIG. 16 schematically illustrates a structure comprising a LinearFeedback Shift Register (LFSR) with generator polynomial x⁻⁷+x⁻⁴+1 wherethe structure is used to generate a pseudo-random bit sequence, butother polynomials could be used. The register contains seven elementslabelled X¹ to X⁷. In FIG. 17 the source of randomness for the phaserandomizer, enclosed by dotted lines, is labelled b7 and is a bit streamdrawn from the seventh element X⁷ in the register. The sources ofrandomness for the cyclic shift randomizer, enclosed by dashed lines,are labelled b1, b2, b3, and are three-bit streams drawn from the first,second and third elements of the register. This breaks the strongcorrelations between the randomness sources for the phase and cyclicshift randomizers.

The decreased correlation between the tapped sequences is achieved bychoosing the source of randomness for a first sequence to depend on afirst set of elements in the LFSR register, and to choose the sources ofrandomness for a second sequence to depend on a second set of elementsof the register, such that the first and second sets arenon-overlapping. The respective set may comprise one element, producinga binary sequence, or a plurality of sets, producing a higher ordersequence, in any combination.

Although binary phase randomization is the simplest phase randomizationtechnique, it is possible to use quaternary or higher order phaserandomization techniques. As an illustration, in the case of quaternaryphase randomization, for each occurrence of an On waveform, a randomlychosen phase of either 0, 90, 180 or 270 degrees is applied to said Onwaveform. Thus, it is necessary to choose randomly among 4 phases. Thiscan be achieved by feeding bitstreams b1 and b2, drawn from elements 1and 2 of the register, to the phase randomizer, and feeding bitstreamsb5, b6, b7 drawn from elements 5, 6 and 7 of the register, to the cyclicshift randomizer. Once again, the key is that the two sets of elementsof the register, namely {1,2} (used for phase randomization) and {5,6,7}(used for cyclic shift randomization) are non-overlapping.

FIG. 19 is a flow chart schematically illustrating methods of thisdisclosure. The method is for transmitting an On-Off Keying, OOK, signalwhich comprises an ON waveform and an OFF waveform forming a patternrepresenting transmitted information. A basic baseband waveform isobtained 1900. The obtaining 1900 of the basic baseband waveform maycomprise generating an Orthogonal Frequency Division Multiplex signalmimicking a desired baseband waveform. The basic baseband waveform isscrambled 1902 by applying a first binary randomised sequence where oneof the binary values cause transformation to a complex conjugate. Thescrambling 1902 of the basic baseband waveform may further compriseapplying a second binary randomised sequence where binary values applyphase rotations which are mutually separated by π. The first randomisedsequence may be generated in a shift register mechanism representing afirst polynomial and the second randomised sequence may be generated ina shift mechanism representing a second polynomial different from thefirst polynomial. The shift register mechanism may use a single shiftregister for the generation of both the first and the second binaryrandomised sequences, where the first binary randomised sequence istapped at a first position of the single shift register and the secondbinary randomised sequence is tapped at a second position of the singleshift register, and the first and second positions of the single shiftregister are different.

The information to be transmitted is modulated 1904 by applying thescrambled basic baseband waveform for the ON waveform and applying nowaveform for the OFF waveform. The modulated information is thentransmitted 1906.

FIG. 20 is a block diagram schematically illustrating a network node2000, e.g. an access point, according to an embodiment. The network nodecomprises an antenna arrangement 2002, a receiver 2004 connected to theantenna arrangement 2002, a transmitter 2006 connected to the antennaarrangement 2002, a processing element 2008 which may comprise one ormore circuits, one or more input interfaces 2010 and one or more outputinterfaces 2012. The interfaces 2010, 2012 can be operator interfacesand/or signal interfaces, e.g. electrical or optical. The network node2000 is arranged to operate in a cellular communication network. Inparticular, by the processing element 2008 being arranged to perform thefeatures demonstrated with reference to FIG. 19, the network node 2000is capable of efficiently providing WUPs and be implemented with lowcomplexity. The processing element 2008 can also fulfill a multitude oftasks, ranging from signal processing to enable reception andtransmission since it is connected to the receiver 2004 and transmitter2006, executing applications, controlling the interfaces 2010, 2012,etc.

The methods according to the present disclosure is suitable forimplementation with aid of processing means, such as computers and/orprocessors, especially for the case where the processing element 2008demonstrated above comprises a processor handling WUP provision.Therefore, there is provided computer programs, comprising instructionsarranged to cause the processing means, processor, or computer toperform the steps of any of the methods according to any of the featuresdescribed with reference to FIG. 19. The computer programs preferablycomprise program code which is stored on a computer readable medium2100, as illustrated in FIG. 21, which can be loaded and executed by aprocessing means, processor, or computer 2102 to cause it to perform themethods, respectively, according to embodiments of the presentdisclosure, preferably as any of the features described with referenceto FIG. 19. The computer 2102 and computer program product 2100 can bearranged to execute the program code sequentially where actions of theany of the methods are performed stepwise or perform the methods on areal-time basis. The processing means, processor, or computer 2102 ispreferably what normally is referred to as an embedded system. Thus, thedepicted computer readable medium 2100 and computer 2102 in FIG. 21should be construed to be for illustrative purposes only to provideunderstanding of the principle, and not to be construed as any directillustration of the elements.

1. A method of transmitting an On-Off Keying, OOK, signal having an ONwaveform and an OFF waveform forming a pattern representing transmittedinformation, the method comprising: scrambling a baseband waveform by atleast one of: applying a first binary randomised sequence where at leastone of the binary values of the first binary randomised sequence causestransformation of the baseband waveform to a complex conjugate of thebaseband waveform; and applying a second binary randomised sequencewhere binary values apply phase rotations which are mutually separatedby a predetermined amount; modulating the information to be transmittedby applying the scrambled baseband waveform for the ON waveform andapplying no waveform for the OFF waveform; and transmitting themodulated information.
 2. The method of claim 1, further comprisingobtaining the baseband waveform by generating an Orthogonal FrequencyDivision Multiplexing (OFDM) signal mimicking a desired basebandwaveform, wherein the OFDM signal has a same envelope as the basebandwaveform and has a different spectral content than the basebandwaveform.
 3. The method of claim 2, wherein the desired basebandwaveform corresponds to a multicarrier on-off keying, MC-OOK, symbol. 4.The method of claim 1, wherein the first randomised sequence isgenerated in a shift register mechanism representing a first polynomialand the second randomised sequence is generated in a shift registermechanism representing a second polynomial different from the firstpolynomial.
 5. The method of claim 4, wherein the shift registermechanism uses a single shift register for the generation of both thefirst and the second binary randomised sequences, where the first binaryrandomised sequence is tapped at a first position of the single shiftregister and the second binary randomised sequence is tapped at a secondposition of the single shift register, and the first and secondpositions of the single shift register are different.
 6. A transmitterfor transmitting an On-Off Keying, OOK, signal which comprises an ONwaveform and an OFF waveform forming a pattern representing transmittedinformation, the transmitter comprising: a scrambler configured toscramble a baseband waveform by at least one of: applying a first binaryrandomised sequence where at least one of the binary values of the firstbinary randomised sequence causes transformation of the basebandwaveform to a complex conjugate of the baseband waveform; and applying asecond binary randomised sequence where binary values apply phaserotations which are mutually separated by a predetermined amount; amodulator configured to modulate the information to be transmitted byapplying the scrambled baseband waveform for the ON waveform andapplying no waveform for the OFF waveform; and a transmitter circuitconfigured to transmit the modulated information.
 7. The transmitter ofclaim 6, further comprising a baseband waveform generator, wherein thebaseband waveform generator is configured to generate a basebandwaveform as an Orthogonal Frequency Division Multiplex (OFDM) signalmimicking a desired baseband waveform, wherein the OFDM signal has asame envelope as the baseband waveform and has a different spectralcontent than the baseband waveform.
 8. The transmitter of claim 7,wherein the desired baseband waveform corresponds to a multicarrieron-off keying, MC-OOK, symbol.
 9. The transmitter of claim 6, whereinthe first randomised sequence is generated in a shift register mechanismrepresenting a first polynomial and the second randomised sequence isgenerated in a shift register mechanism representing a second polynomialdifferent from the first polynomial.
 10. The transmitter of claim 9,further comprising a shift register, wherein the shift registermechanism uses the shift register for the generation of both the firstand the second binary randomised sequences, where the first binaryrandomised sequence is tapped at a first position of the shift registerand the second binary randomised sequence is tapped at a second positionof the shift register, and the first and second positions of the shiftregister are different.
 11. An apparatus for generating sequences, theapparatus comprising: a shift register; a feedback structure connectedto the shift register arranged to define a linear feedback shiftregister according to a polynomial; a first output configured to collectone or more state values from a first group of elements of the shiftregister, the one or more state values from the first group forming avalue of a first sequence; a second output configured to collect one ormore state values from a second group of elements of the shift register,the one or more state values from the second group forming a value of asecond sequence, no element of the second group belonging to the firstgroup, and configured to one of: collect state values from the secondgroup of elements, the second group comprising a plurality of elementsof the shift register such that the second sequence comprises symbolshaving more than two possible values; and collect state values from thesecond group of elements, where the second group comprises a singleelement of the shift register; and a third output configured to apply abinary randomised sequence to the second sequence to causetransformation of the second sequence to a complex conjugate of thesecond sequence.
 12. The structure of claim 11, wherein the first outputis configured to collect state values from the first group of elementscomprising a plurality of elements of the shift register such that thefirst sequence comprises symbols having more than two possible values.13. The structure of claim 11, wherein the first sequence is a binarysequence.
 14. The structure of claim 13, wherein the first output isconfigured to collect state values from the first group of elements,where the first group comprises a single element of the shift register.